"JOURNAL OF RADIO ELECTRONICS" N 11, 2012 |
Modeling and Validation of Loose Coupler by Using DGS in Branch line Coupler
^{1}Tamasi Moyra, ^{2}Susanta Kumar Parui, ^{2}Santanu Das
^{1}Department of Electronics and Communication Engineering,
National Institute of Technology, Agartala
^{2}Department of Electronics and Telecommunication Engineering,
Bengal Engineering and Science University, Shibpur, www.becs.ac.in, India
Received November 9, 2012
Abstract. A novel planar 10 dB loose branch line coupler is proposed for application to the 2.5 GHz centre frequency. This proposed coupler is implemented with rectangular ring headed dumbbell shaped Defect Ground Structure (DGS) along with conventional microstrip transmission line. Design of this conventional branch line coupler with DGS provides more design flexibility. Use of DGS underneath the microstrip line increases the electrical length of microstrip line, provides slow wave characteristics and increases the impedance of the microstrip line. In this paper one high impedance microstrip line is easily implemented by using proposed DGS structure which is required for designing the loose coupler. Finally, the compact branch line 10 dB loose coupler is designed, fabricated and measured. The experimental results are in good agreement with predicted simulated values.
Keywords: branch line coupler, Defect Ground Structure (DGS), 10 dB loose coupling, microstrip line.
I. INTRODUCTION
The branch-line coupler [1] plays an important role in microwave and millimeter wave circuits. There are lots of applications of hybrid branch-line 3-dB or 6-dB tight couplers in our modern microwave and millimeter wave communication systems. Those tight couplers can be easily designed using transmission line in a conventional way. But design of loose coupler is quite different.
A transmission line with etched defects on metallic ground plane such as two-dimensional photonic Band Gap (PBG) and one-dimensional Defected Ground Structure (DGS) has been studied in microwave and millimeter-wave frequency ranges [1-3]. Applications of a microstrip line with DGS structure include slow-wave structure, harmonic rejections with compact dimensions and low-loss characteristic, various circuit design, and so on [4]-[6]. Etched defects on metallic ground plane of a microstrip line provide higher effective permittivity and characteristic impedance than those of the conventional microstrip line due to increase of the electric length and effective inductance of transmission lines [4-9]. Microstrip line with DGS increases the group velocity delay due to the steep phase characteristic. Delay of the group velocity reduces the dimension of distributed components in RF and microwave integrated circuits.
In this paper, one branch-line coupler with rectangular ring headed dumbbell shape DGS is proposed in order to implement loose coupling characteristics of 10 dB, which requires for the realization of high impedance line. Requirement of the high impedance line section faces with restrictions such as impractical very narrow transmission line width in implementation of designed circuits. In this paper, the DGS structures are used to implement the high impedance line section. Use of the DGS section makes it easy to control the characteristic impedance of microstrip line and provides design flexibility. Since DGS section can increase the electrical length and effective inductance of microstrip line hence the conductor width with DGS section for a determined characteristic impedance is wider than that of conventional microstrip line. The coupling can be controlled by changing the physical dimensions of the DGS and adjusting the length and width of the microstrip line. Finally, a 10-dB loose branch-line coupler operating at 2.5 GHz is optimally designed, fabricated and measured.
II. GENERAL STUDY AND CALCULATION OF IMPEDANCES
(a) General Study of Branch-line Coupler:
Fig. 1 shows a branch-line coupler. It consists of two quarter-wave-long () transmission line sections of characteristic impedance each, connected by two shunt branches. The shunt branches are quarter-wave-long () transmission line sections of characteristic impedance each. By selecting the appropriate values of and, the circuit can be made to operate like a directional coupler.
Fig. 1. Layout of a branch-line coupler in planar circuit configuration
At the center frequency the scattering parameters of a branch-line coupler are given by
Where, denotes the impedance of various ports of a branch-line coupler. The scattering parameters of a branch-line coupler also satisfy the following condition, which follows from the principle of conservation of energy:
Where, it is assumed that S_{11}=S_{41}=1. Substituting the values of scattering parameters from equations (1) and (2) it is found that and should satisfy the following condition:
A branch-line coupler as shown in Fig.1 has two planes of symmetry. The scattering matrix of a branch line coupler can therefore be expressed as,
The characteristic impedances of the main-line and shunt branches of a branch-line can be computed using equations (1) and (2) as
and
Z_{os }and Z_{op} are the required main line and shunt branch line characteristic impedances of any branch-line coupler.
(b) Calculation of Z_{os }and Z_{op} for 10-dB coupler:
Consider all ports are matched to 50 microstrip transmission line i.e. . For 10 dB branch line coupler coupling from port 1(Input port) to port 3 (coupled port ) is 10 dB.
i.e.
or,
or, ……………………………………(10 a)
Now, from equation (5) , it can be obtained
………….......…………………..(10 b)
Using equation (8) and (9), we have,
………………...……………...…….(11 a)
and ……………….…………………………..(11 b)
III. EFFECT OF DGS ON CHARACTERISTIC IMPEDANCE
One microstrip transmission line of length 16.4mm and width 3mm with FR4 substrate (of dielectric constant 4.4 and substrate height 1.59mm with negligible loss tangent) provides 50characteristic impedance at 2.5 GHz. This characteristic impedance can be controlled by introducing DGS underneath a microstrip line. For simplicity, let there is a rectangular ring headed dumbbell shaped DGS underneath a 50 microstrip line as shown in Fig. 2(a) and the simulated magnitude responses or scattering parameters are shown in Fig. 2(b). Simulation has been done with IE3D electromagnetic simulator. As an example one rectangular ring dumbbell DGS of head length, a = 8mm and breadth, b = 6 mm and width, c = 0.5mm and two heads are connected with transverse slot of length 4mm and width 0.5mm is etched in the ground plane of the microstrip line. One remarkable advantage of using the DGS under the microstrip line is that it can increase the characteristic impedance by the additional effective inductance generated by the loop of DGS structure. The addition of this extra inductance causes the characteristic impedance of the microstrip line to be much higher than that of a conventional microstrip line with the same conductor width.
Fig. 2(a). Rectangular ring dumbbell DGS
under 50 microstrip line
Fig. 2(b). Scattering parameters
The equivalent circuit of the microstrip line with DGS is shown in Fig.3. Then, the equivalent characteristic impedance and electrical length of the microstrip line with DGS are determined [9] from the S-parameters calculated by simulation.
Fig.3. Equivalent circuit of the DGS section, and Z_{ }_{0} is the reference impedance.
The S_{ }_{21} can be expressed as following:
………………………………………..………(12)
The variable m is:
………………………………………..……….…….(13)
The constant θ is the electrical length. Then, m and θ can be derived from the magnitude and phase (φ _{21}) of S_{21} :
……………………………..…………...…..(14)
…....……………… ….…..(15)
Then, the equivalent characteristic impedance is:…………………………… .…..(16)
When the electrical length θ is quarter wavelength, the equivalent characteristic impedance of the microstrip line with DGS is calculated as following:
………………………………………....…..……(17)
…………………………………………………..….(18)
The variable Z _{in} is the input impedance toward the DGS section and Γ denotes the input reflect coefficient.
From the above concept and equations it is possible to find the effective characteristic impedance of the microstrip line with DGS. Now, in the taken example in Fig. 2(a) the 3mm width microstrip line provides 50 characteristic impedance without DGS at operating frequency 2.5 GHz. i.e. Z_{0} = 50. But introducing DGS provides the scattering response as Fig. 2(b), from Fig. 2(b) and equation (17) and (18) it can be obtained the effective characteristic impedance of the microstrip line with DGS is, Z_{c} = 69.775.
The effective characteristic impedance can be tuned by varying the dimension of one parameter keeping other constant. The following Table 1 shows the different values of effective impedance, Zc with different values of defected head length, a.
Table 1: Variation of Zc with head length a (with line impedance 50 )
Length, a (mm)
4
6
8
10
Line imp, Zc ()
58.8004
62.3951
69.775
88.298
IV. DESIGN PROCEDURE OF 10 dB COUPLER
From the above analysis in section II, it has been observed that there is the requirement of Z_{0s} = 47.434 characteristic impedance transmission line for the main branch and Z_{0p} = 150 characteristic impedance transmission line for shunt branch line. The 10-dB branch line loose coupler has been designed and fabricated on FR4 substrate of dielectric constant 4.4 and substrate height 1.59mm with negligible loss tangent. The low characteristic impedance 47.434 value of the main line can be easily implemented with the help of conventional microstrip line of length 16.4mm with 3.29 mm width at 2.5 GHz. But there is requirement of almost 17mm length and 0.17 mm width microstrip line for the design of150 characteristic impedance for shunt branch line. The fabrication of this too narrow microstrip line is tough enough and almost impossible. Therefore, an arbitrary rectangular ring headed dumbbell DGS has been introduced underneath a practical width of 0.6mm microstrip line for designing high impedance shunt branch line as shown in the Fig. 4(a) and the scattering parameters are shown in Fig. 4(b).
(a)
(b)
Fig. 4. (a) proposed DGS, (b) Scattering response
From the above concept obtained from the section III, the effective characteristic impedance of microstrip line obtained from the above DGS structure is 165.451. Now, the effective characteristic impedance of microstrip line can be tuned by changing the dimension of any parameter of DGS keeping others constant. Considering, width (b) of the ring head is variable keeping other parameters constant. Then variation of the reflection coefficient and the characteristic impedance is shown in Table 2.
Table 2 Variation of and Z_{c} with ‘b’: with line impedance 119.47
Ring width, b (mm)
Reflection coefficient
Char. Impedance, Z_{c}_{ } ()
7
1.467
177.686
6
1.567
164.451
4
1.833
142.533
Fig. 5 shows the variation of the characteristic impedance Z_{c} with ring width, b as follows:
Fig. 5. Ring breath, ‘b’ Vs. characteristic impedance ‘Z_{c}’
From the above Fig. 5 it is observed that there is the requirement of ring width, b =4.65mm to obtain the 150 characteristic impedance. Therefore, the proposed structure of 10 dB branch line coupler is shown in Fig. 6(a) as follows:
Fig. 6(a). Proposed 10 dB branch line coupler
The required dimensions of the proposed rectangular ring headed dumbbell DGS structure for high impedance, 150 shunt branch line are a =8mm, b = 4.65mm, c = 0.5mm and the two heads are separated by 2mm long, 0.5mm width transverse slot. The others dimensions are L_{1} = 16.4mm, W_{1} =3.29mm,W_{2} = 3mm, L_{2} = 17mm and W_{3} = 0.6mm. The above designed structure of 10 dB loose coupler is fabricated on FR4 substrate and simulated by MoM based IE3D electromagnetic simulator and the scattering responses are shown in Fig. 6(b).
Fig. 6(b). Scattering parameters
The 10-dB loose branch line coupler is designed for the operating frequency 2.5 GHz. From the characteristic response, shown in Fig. 6(b), it is obtained that the coupling from input port to coupled port i.e. from port 1 to port 3 (i.e. S_{31}) is 10 dB at 2.5 GHz. Now, to calculate the fractional band width (FBW) at 10 dB, the characteristic response is re-represented for small frequency span as shown in Fig. 6(c) as follows:
Fig. 6(c). Scattering parameters around center frequency
The above response shows that the structure provides 10 dB coupling from lower frequency, f_{1} = 1.9GHz to higher frequency, f_{2} = 3.2 GHz around center frequency, f_{0} = 2.5 GHz with negligible tolerance. Therefore, the fractional bandwidth [FBW= ((f_{1}-f_{2})/f_{0})100%] of the proposed 10-dB branch line coupler is 52% with zero tolerance.
The following table, Table: 3 shows the FBWs for different considerable tolerances of coupling.
Table: 3FBWs for different considerable tolerances.
Tolerance
0%
5%
10%
20%
FBW (%)
52
57
60.8
87.2
V. MEASUREMENT AND DISCUSSION
The proposed structure has been fabricated with FR4 substrate. The photonic view of the 10 dB coupler is shown in the following Fig. 7.
(a) (b)
Fig. 7. Photonic Views (a) Top Plane (b) Ground Plane
The proposed 10 dB branch line coupler has been measured with an Agilent make vector network analyzer of model N5230A. The measurement responses of the scattering parameters are shown in the following Figure 8.
Fig. 8. Scattering Parameters (Measurement responses)
The above responses show that there is a 10.4 dB coupling between input port and coupled port (S_{31}) at operating frequency 2.5 GHz. Thus, the proposed structure behaves as 10 dB coupler and provides almost 60 % FBW with 5% tolerance. The different scattering parameter for simulated and measurement results are shown in Fig. 9.
(a) (b)
Fig. 9. Scattering Parameters (a) S_{11} & S_{31, }(b) S_{21} & S_{41}
From the above analysis with simulated and measurement responses it is observed that the proposed branch line coupler with rectangular ring headed DGS acts as a loose coupler and provides 10dB coupling at the operating frequency 2.5 GHz.
VI. CONCLUSION
Generally, with the help of branch line tight coupler such as 3dB, 6dB etc are designed. In this paper a new concept for designing of loose coupler has been established and as an example one 10-dB branch line coupler is designed. Here, the main branch line is obtained by simple conventional microstrip line and the high impedance shunt branch line is formed by introducing DGS underneath a conventional microstrip line. Adding DGS introduces some inductance and increases the effective electric length of the microstrip line and provides slow-wave characteristics. Finally, one 10-dB branch line coupler is designed, fabricated and measured and there is a good agreement between simulated and measurement results have been obtained. However, though 10-dB branch line coupler is designed by using the proposed concept but utilizing the same concept any loose coupler, such as 15dB, 20 dB etc can easily be obtained.
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